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exar corporation, 48720 kato road, fremont, ca 94538 ? (510) 668-7000 ? fax (510) 668-7017 ? www.exar.com xrd98l59 ccd image digitizers with cds, pga and 10-bit a/d january 2001-2 features ? 10-bit resolution adc ? 20mhz sampling rate ? programmable gain: 6db to 38db pga (2x to 80x) ? improved digitally controlled offset-calibration with pixel averager and hot pixel clipper ? dns filter removes black level digital noise ? widest black level calibration range at maximum gain ? manual control of offset dac via serial port for use with high speed scanners ? 2ns/step programmable aperture delay on spix and sblk ? single 2.7v to 3.6v power supply ? low power for battery operation:120mw @ v dd =3v applications ? digital still cameras ? digital camcorders ? pc video cameras ? cctv/security cameras ? industrial/medical cameras ? 2d bar code readers ? high speed scanners ? digital copiers general description the xrd98l59 is a complete low power ccd image digitizer for digital, motion and still cameras. the product includes a high bandwidth differential corre- lated double sampler (cds), 8-bit digitally program- mable gain amplifier (pga), 10-bit analog-to-digital converter (adc) and improved digitally controlled black level auto-calibration circuitry with pixel averager hot pixel clipper, and a dns filter. the correlated double sampler (cds) subtracts the ccd output signal black level from the video level. common mode signal and power supply noise are rejected by the differential cds input stage. the pga is digitally controlled with 8-bit resolution on a linear db scale, resulting in a gain range of 6db to 38db with 0.125db per lsb of the gain code. the auto calibration circuit compensates for any inter- nal offset of the xrd98l59 as well as black level offset from the ccd. the pga and black level auto-calibration are con- trolled through a simple 3-wire serial interface. the timing circuitry is designed to enable users to select a wide variety of available ccd and image sensors for their applications. the xrd98l59 has direct access to the adc input for digitizing other analog signals. the xrd98l59 is packaged in 28-lead surface mount tssop to reduce space and weight, and is suitable for hand-held and portable applications. ? 5 a typical stand by mode current ? three-state digital outputs ? 2,000v esd protection ? 28-pin tssop package rev. 2.00 ordering information operating maximum part no. package tem perature range power supply sampling rate xrd98l59aig 28-lead tssop -40c to 85c 3.0v 20 msps
xrd98l59 2 rev. 2.00 figure 1. xrd98l59 block diagram cds 10-bit adc hot pixel clipper pixel averager + - + coarse accumulator fine accumulator offset calibration logic 10 pga1 reg serial interface and registers internal clock generator pga2 calibration mode target offset code gain code clock control avdd dvdd agnd dgnd ovdd ognd db[9:0] ccdin vrt vrb refin spix sblk clamp cal sclk sdi load pd 4-bit 10-bit + + 10 power down 400 140 60 agnd avdd power down manual dac control black level offset calibration loop adcin cdac fdac dns filter
3 rev. 2.00 xrd98l59 pin configuration 28-lead tssop pin description xrd98l59 spix cal clam p

ccdin refin agnd vrb db7 db8 db9 ovdd db6 db5 dvdd vrt sclk load sdi pd dgnd avdd sblk db1 db0 db2 db3 db4 ognd pin # symbol description 1ov dd digital output power supply (< av dd ) 2 db5 adc output 3 db6 adc output 4 db7 adc output 5 db8 adc output 6 db9 adc output, msb 7dv dd digital power supply (must = av dd ) 8 dgnd digital ground. connect to agnd 9 sclk shift clock. latches sdi data on serial port 10 sdi serial data input. serial port 11 load data load. serial port 12 pd power down, active high 13 vrt top adc reference. sets full scale of adc 14 av dd analog v dd 15 ccd in cds inverting input. connect through capacitor to ccd signal 16 ref in reference input (cds non inverting input). connect through capacitor to ccd ground 17 agnd analog ground 18 vrb bottom adc reference. sets zero for adc. 19 cal optical black (ob) clamp 20 clamp cds dc restore clamp 21 spix sample video pixel (cds clock) 22 sblk sample black reference (cds clock) 23 db0 adc output, lsb 24 db1 adc output 25 db2 adc output 26 db3 adc output 27 db4 adc output 28 ognd digital output gnd. connect to agnd
xrd98l59 4 rev. 2.00 dc electrical characteristics ? xrd98l59 unless otherwise specified: ov dd = dv dd = av dd = 3.0v, pixel rate = 20msps, t a = 25c symbol parameter min. typ. max. unit conditions cds performance cdsv in input range 800 mv pp pixel (v black - v video ), (see figure 2) v dark maximum dark voltage offset 150 mv at any gain. (see figure 2) r on clamp on resistance 120 ? pga parameters av min minimum gain 3.5 5 6.5 db av max maximum gain 36 db pga n resolution 8 bits transfer function is linear steps in db (1lsb = 0.125db) adc parameters (measured in adcin test mode), sdi = 0100 0000 0101 b adc n resolution 10 bits f s max sample rate 20 msps dnl differential non-linearity -1 +0.75 1.5 lsb ezs zero scale error +25 mv measured relative to v rb efs full scale error 1.5 % fs v in dc input range gnd av dd vav in of the adc can swing from agnd to av dd . input range is limited by the output swing of the pga. ? v ref adc reference voltage 2 v v rb self bias v rb 0.2 0.3 0.4 v v rt self bias v rt 2.0 2.3 2.6 v ( v rb = av dd 10 ) ( v rb = av dd 1.30 )
5 rev. 2.00 xrd98l59 dc electrical characteristics - xrd98l59 (cont'd) unless otherwise specified: ov dd = dv dd = av dd = 3.0v, pixel rate = 20msps, t a = 25 c symbol parameter min. typ. max. unit conditions system specifications dnl s system dnl -1 +0.75 1.5 lsb no missing codes, monotonic inl smin system inl @ minimum gain 2 lsb inl error is dominated by cds/pga linearity inl smax system inl @ maximum gain 2 lsb inl error is dominated by cds/pga linearity e n maxav input referred noise @ 0.2 mv rms gain code = ffh max gain e n minav input referred noise @ 0.7 mv rms gain code = 00 h min gain latency pipeline delay 4 cycles digital inputs v ih digital input high voltage 2.1 v v il digital input low voltage 0.5 v i l dc leakage current 5 av in = gnd or v dd c in input capacitance 5 pf digital outputs v oh digital output high voltage ov dd -0.5 v while sourcing 2ma v ol digital output low voltage 0.5 v while sinking 2ma i oz high ? z leakage -10 10 a oe = 0 or pd = 1 output = ognd or odv dd
xrd98l59 6 rev. 2.00 dc electrical characteristics - xrd98l59 (cont'd) unless otherwise specified: ov dd = dv dd = av dd = 3.0v, pixel rate = 20msps, t a = 25 c symbol parameter min. typ. max. unit conditions digital i/o timing t dl data valid delay 28 35 ns t pw1 pulse width of spix 10 ns t pw2 pulse width of sblk 10 ns t pix pixel period 50 ns t bk sample black (sblk), 3.5 ns sblk delay = 000 aperture delay t vd sample video (spix), 2.7 ns spix delay = 000 aperture delay t sclk shift clock period 100 ns t set shift register setup time 10 ns t hold shift register hold time 0 ns t l1 load set-up time 10 ns t l2 load hold time 10 ns power supplies av dd analog supply voltage 2.7 3.0 3.6 v dv dd digital supply voltage 2.7 3.0 3.6 v set dv dd = av dd ov dd digital output supply voltage 2.7 3.0 3.6 v ov dd < av dd i dd supply current 40 55 ma ov dd = av dd = dv dd =3.0v, includes reference current i ddpd power down supply current 5 25 a pd = 1, clocked
7 rev. 2.00 xrd98l59 ccd waveform v black v video cds v in v dark figure 2. definition of terms for v out of the ccd waveform: cdsv in = (v black - v video ) absolute maximum ratings (t a = +25 c unless otherwise noted) 1, 2, 3 v dd to gnd ..................................................... +7.0v v rt & v rb .................................... v dd +0.5 to gnd -0.5v v in ................................................... v dd +0.5 to gnd -0.5v all inputs .............................. v dd +0.5 to gnd -0.5v all outputs ............................ v dd +0.5 to gnd -0.5v storage temperature .......................... -65 c to 150 c lead temperature (soldering 10 seconds) ..... 300 c maximum junction temperature .................... 150 c package power dissipation ratings (t a = +70 c) tssop ....................................... ja = 90 c/w esd ........................................................ 2000v notes: 1 stresses above those listed as ? absolute maximum ratings ? may cause permanent damage to the device. this is a stress rating only and functional operation at or above this specification is not implied. exposure to maximum rating conditions for extended periods may affect device reliability. 2 any input pin which can see a value outside the absolute maximum ratings should be protected by schottky diode clamps from input pin to the supplies. all inputs have protection diodes which will protect the device from short transients outside the supplies of less than 100ma for less than 100s. 3 v dd refers to av dd , ov dd and dv dd . gnd refers to agnd, ognd and dgnd.
xrd98l59 8 rev. 2.00 serial interface the xrd98l59 uses a three wire serial interface (load, sdi & sclk) to access the programmable features and controls of the chip.the serial interface uses a 12-bit shift register. the first 4 bits shifted in are the address bits, the next 8 bits are the data bits. the address bits select which of the internal registers will receive the 8 data bits. there is no checking or read back of the address bits to ensure a valid register is written to. if the address bits select an undefined register, the data will be discarded. sclk sdi load time a3 a2 a1 a0 d7 d6 d5 d4 d3 d2 d1 d0 t1 t2 t12 t11 ? t l1 t l2 t sclk t set t hold msb lsb serial port procedures 1) set load pin low to enable shift register. 2) shift in 4 address bits (msb first), followed by 8 data bits (msb first). 3) set load pin high to transfer data from the shift register to the serial interface register array. for optimum image quality, do not run the serial port during active video. serial port clocking can couple into the signal path and degrade accuracy. also, do not continuously run sclk. reseting the xrd98l59 is recommended after initial power-up. it is generally good practice to reset the xrd98l59 because the serial data may be forced to an unknown state during power supply cycling by the digital asic. figure 3. serial interface timing diagram
9 rev. 2.00 xrd98l59 re g ister arra y sdi sclk load re g ister select data input address decoder address bits data bits d0 d1 d2 d3 d4 d5 d6 d7 a0 a1 a2 a3 msb lsb figure 4. serial interface timing diagram address bits data bits reg. name a3 a2 a1 a0 d7 d6 d5 d4 d3 d2 d1 d0 gain 0 0 0 0 gain [7:0] target offset 0 0 0 1 offset [5:0] delay 0 0 1 0 sblk delay [2:0] spix delay[2:0] exar test clock 0 0 1 1 rst re j exar test clamp opt sblk pol spixpol clamp pol cal pol control 0 1 0 0 dela y test adcin pd oe calibration 0 1 0 1 cal hold speed up dns 1 dns 0 man dac fdac (msb) 0 1 1 0 fdac [9:2] fdac (lsb) 0 1 1 1 fdac [1:0] cdac 1 0 0 0 cdac [3:0] not used reset 1 1 1 1 reset table 1. serial interface register address map
xrd98l59 10 rev. 2.00 d7 d6 d5 d4 d3 d2 d1 d0 gain[7:0] 0 0 0 0 0 0 0 0 minimum gain (6 db) * 1 1 1 1 1 1 1 1 maximum gain (38 db) table 2. gain register bit assignment (address 0000) d7 d6 d5 d4 d3 d2 d1 d0 not used not used offset[5:0] 0 0 0 0 0 0 do not use (00h) 0 0 0 0 0 1 do not use (01h) 0 0 0 0 1 0 minimum offset (02h) 1 0 0 0 0 0 default offset (20h) * 1 1 1 1 1 1 maximum offset (3fh) table 3. target offset register bit assignment (address 0001) for pga d7 d6 d5 d4 d3 d2 d1 d0 sblk delay[2:0] spix delay[2:0] exar test 0 0 0 min delay * 0 0 0 min delay * 0 0 default 1 1 1 max delay 1 1 1 max delay 01, 10, 11 do not use table 4. delay register bit assignment (address 0010) d7 d6 d5 d4 d3 d2 d1 d0 not used rst rej exar test clamp opt sblk pol spix pol clamp pol cal pol 0 switch on * 0 default 0 cal only 0 active low * 0 active low * 0 active low * 0 active low * 1 clocked 1 do not use 1 clamp+cal * 1 active high 1 active high 1 active high 1 active high table 5. clock register bit assignment (address 0011) for spix or sblk d7 d6 d5 d4 d3 d2 d1 d0 not used not used not used not used delay test adcin pd oe 0 test off * 0 test off * 0 convert * 0 outputs off 1 test on 1 test on 1 power down 1 outputs on * table 6. control register bit assignment (address 0100) table 7. calibration register bit assignment (address 0101) d7 d6 d5 d4 d3 d2 d1 d0 not used not used not used cal hold speed up dns1 dns0 man dac 0 cal active* 0 speed up off 0 dns off 0 = wide* 0 automatic* 1 hold value 1 speed up on* 1 dns on* 1 = narrow 1 manual note: * shading indicates default values after power up or reset. the xrd98l59 does not reset the registers to default va lue after pd.
11 rev. 2.00 xrd98l59 table 8. fdac (msb) register bit assignment (address 0110) d7 d6 d5 d4 d3 d2 d1 d0 fdac[9:2] 1 1 1 1 1 1 1 1 max pos offset 1 0 0 0 0 0 0 0 zero offset 0 0 0 0 0 0 0 0 max neg offset * d7 d6 d5 d4 d3 d2 d1 d0 not used not used not used not used not used not used fdac[1:0] 1 1 max pos offset 0 0 max neg offset * table 9. fdac (lsb) register bit assignment (address 0111) d7 d6 d5 d4 d3 d2 d1 d0 not used not used not used not used cdac[3:0] 1 1 1 1 1 0 1 1 max pos offset zero offset +50 mv 0 0 0 0 max ne g offset * -137.5 mv table 10. cdac register bit assignment (address 1000) d7 d6 d5 d4 d3 d2 d1 d0 not used not used not used not used not used not used not used reset 0 normal * 1 reset chip table 11. reset register bit assignment (address 1111) note: * shading indicates default values after power up or reset. the xrd98l59 does not reset the registers to default value after pd.
xrd98l59 12 rev. 2.00 correlated double sample/hold (cds) the function of the cds block is to sense the voltage difference between the black level and video level for each pixel. the pga then amplifies this difference to the desired level for the adc. the cds and pga are fully differential. the pga output is converted to a single ended signal and fed to the adc. the ccdin pin (cds inverting input) should be connected, via a capacitor, to the ccd output signal. the refin pin (cds non- inverting input) should be connected, via a capacitor, to the ccd ? common ? voltage. this is typically the ccd reference output or ground. at the beginning (or end) of every video line, the dc restore switch forces one side of the external capacitors to an internal vbias1 level (approximately 0.8v). the dc restore switch is controlled by the combination of the clamp signal anded with the 2 clock. (see figure 5). during the black reference phase of each ccd pixel the 1 (sample black reference) switches are turned on, shorting the pga1 inputs to a second bias level. the coarse offset dac adds an adjustment to the vbias2 level to cancel offset in the ccd signal. when the 1 switches turn off, the pixel black reference(v black ) is sampled on the internal reference sample capacitors, and the pga is ready to gain up the ccd video signal. during the video phase of each ccd pixel the difference between the pixel black reference level and video level is transmitted through the internal reference sample ca- pacitors and converted to a fully differential signal by the pga1 amplifier. at this time the 2 (sample pixel value) switches turn on, and the internal video sample capaci- tors track the amplified difference. figure 5. block diagram of cds and pgas 1 clamp vbias1~0.8v vbias2 refin ccdin pga1 pga2 ccd coarse offset dac pga cds external dc blockin g capacitors internal black sample capacitors ( ~5pf ) reset re j ect switches internal video sample dc restore switches fine offset dac agnd to adc xrd98l59 2 2 capacitors ( ~5pf ) r on 120 ?
13 rev. 2.00 xrd98l59 pixel timing sblk & spix the timing required by the xrd98l59 to sample indi- vidual pixel data from a ccd output is shown below in figure 6. the diagram shows the general relationship of timing signals sblk and spix to the ccd waveform. figure 6. cds timing diagram - proper placement of timing is critical to image quality, sdi=0011 0100 1100 *rst rej is an internally generated signal. table 12. event table for cds timing (sdi=0011 0100 1100) the xrd98l59 was designed to sample any analog ccd waveform. in order to do this the timing signals need to be referenced to the waveform itself, not to the ccd ? s timing generator. event action rstrej disconnects cds inputs from reset noise rstrej connects cds inputs sblk high sample black level spix high sample video level sblk/spix low hold video and black level 1 2 3 4 5 sblk spix ccd in rst rej* pixel black level sample point pixel video level sample point t bk t vd t rst switch open reset pulse reset phase black reference phase video phase 1 2 2 3 4 3 4 55 1 reset reject reset reject switch closed pixel n pixel n + 1 n-3 n-4 db[9:0] t pix t pw1 t pw2 t dl t dl
xrd98l59 14 rev. 2.00 rstrej reduces ccd reset noise by disconnecting the input of the xrd98l59 from the ccd during the ccd reset pulse. rstrej is an internally generated signal. rstrej disconnects the input after the spix and before the sblk sampling events to reject ccd reset noise. the rstrej switch is always closed (the input is always connected) if d6=0 in the clock register (address 0011) of the serial port. for the timing example shown in figure 6, sblk high samples the pixel black level. the actual hold point of the pixel black level occurs after a delay of t bk . t bk is the aperture delay of the sblk timing signal. the polarities of the sblk and spix signals are indepen- dently programmable via the serial port. for the timing example shown in figure 6, spix high samples the pixel video level. the actual hold point of the pixel video level occurs after a delay of t vd . t vd is the aperture delay of the spix timing signal. the polarity of the spix signal is serial port programmable. the function of the cds block, shown in figure 7, is to sense the voltage difference between the black level and video level for each pixel. the cds and pga are fully differential to reject common mode noise. the pga output is converted to a single ended signal, and then fed to the adc. ref in (cds non-inverting input) should be connected, via a capacitor, to the ccd ? common ? voltage. this is typically ccd ground. ccd in (cds inverting input) should be connected, via a capacitor, to the ccd output signal. the external coupling capacitors on ccd in and ref in should be of equal values to minimize gain errors (typically 0.01 f +/-10%). figure 7. block diagram of the cds, reset phase: rstrej switch is open + pga1 - vbias1 ~0.8 external coupling capacitors vbias2 clamp 1 gain register to adc c c d gnd vout c1 c2 c3 + pga2 - + buf - c4 2 rstrej
15 rev. 2.00 xrd98l59 during the video phase of each pixel the 2 switches are closed when spix is active. the difference between the pixel black reference level and video level is transmitted through capacitors c1 & c2. differential amplifier pga1 pga1 vbias1 ~0.8 external coupling capacitors vbias2 clamp in_pos in_neg gain register to adc c c d gnd vout c1 c2 c3 pga2 buf c4 1 2 rstrej + pga1 - vbias1~0.8 external coupling capacitors vbias2 clamp gain register to adc c c d gnd vout c1 c2 c3 + pga2 - + buf - c4 1 2 rstrej figure 9. cds - video phase: 1 switches open, 2 and rstrej switches closed during the black reference phase of each pixel the rstrej switches are closed, allowing the difference between the black reference level voltage and vbias2 to develop across capacitors c1 and c2 (see figure 8). 1 is closed when sblk is active. figure 8. cds - black reference phase: rstrej and 1 switch closed amplifies both cds inputs from ccd in and ref in . the inactive phase of spix turns off the 2 switches, storing the differential pixel value on capacitors c3 & c4 (see figure 9). during the reset phase of each pixel the rstrej switches are turned off, see figure 7, opening the xrd98l59 cds input. this is done to limit reset pulse transients seen by the front end of the xrd98l59.
xrd98l59 16 rev. 2.00 figure 10. timing diagram of the cds clocks and internal signals (rstrej, 1 , , , , , 2, adcclk ) ) ) ) ) sdi = 0011 0100 1100 * digital output data is updated on the falling edge of 2. this update position is affected by the aperture delay of 2. note: aperture delay is not shown ccd rstrej sblk spix 1 2 (internal signals) adclk hold track reset phase black reference phase video phase db[9:0]*
17 rev. 2.00 xrd98l59 d4 d3 d2 2 aperture delay 0 0 0 2.7ns (default) 0 0 1 4.7ns 0 1 0 6.7ns 0 1 1 8.7ns 1 0 0 10.7ns 1 0 1 12.7ns 1 1 0 14.7ns 1 1 1 16.7ns table 14. programmable 2 delays d7 d6 d5 1 aperture delay 0 0 0 3.5ns (default) 0 0 1 5.5ns 0 1 0 7.5ns 0 1 1 9.5ns 1 0 0 11.5ns 1 0 1 13.5ns 1 1 0 15.5ns 1 1 1 17.5ns table 13. programmable 1 delays sblk and spix programmable aperture delay (sdi address = 0010) the positioning of 1 and 2 from figure 10, are opti- mized by using a programmable aperture delay function. 1 and 2 are delayed internally by the amount specified in the serial port. sblk delay (d7:d5) delays the 1 clock and spix delay (d4:d2) delays the 2 clock. the delay is 2ns per lsb. the aperture delays t bk and t vd are added to the programmable aperture delay to determine final positioning. the tables below include the t bk and t vd aperture delays. the aperture delay of 2 also delays the output data bus db[9:0]. digital output data is updated on the falling edge of 2 as shown in figure 10. data is valid after t dl plus the change in 2 aperture delay. for example, if d[4:2] equals 001b, then data is valid at t dl + 2ns. (t dl is shown in figure 6).
xrd98l59 18 rev. 2.00 figure 11. end of line ob pixels used for line calibration mode on a typical ccd array active pixels end of line ob calibration pixels line calibration mode line calibration mode calibrates during the ob pixel output from the ccd at the end of every line. figure 11, shows the outline of a typical ccd area array. the active (white) pixels are shown with the ob (shaded) pixels around the edges. the ob pixels used in line calibration are identified below in figure 11 as the dark shaded ob pixels on the right hand side of the array. line timing: clamp and cal clamp & cal line timing (sdi address = 0011, d4 = 1) the timing needed for line calibration mode is shown in figure 12. the timing signal cal gates the xrd98l59 ? s auto-calibration logic. cal is active during the end of line ob pixels. most timing generators (tg ? s) have signals that define the start of line and end of line ob pixels on the ccd array. cal should always be active on start or the end of line that defines the greatest number of ob pixels possible. the more ob pixels that the xrd98l59 can use for its auto-calibration, the faster it can achieve and maintain calibration. cal and clamp must never be active at the same time. clamp is used to set the input dc bias voltage. (see figure 5).
19 rev. 2.00 xrd98l59 figure 12. example of clamp & cal line calibration mode timing (cal and clamp polarity are serial port programmable) sdi = 0011 0001 0011 line n line n+1 * note: ob = optically black or shielded pixels. active video pixels ob* pixels vertical shift dummy & ob* pixels cal clamp ccd signal active video pixels (horizontal clocking off) min 1 pixel min 1 pixel line timing: cal only cal only line timing (sdi address = 0011, d4 = 0) the timing needed for "cal only" line calibration mode is shown in figure 13. in "cal only" line calibration the timing signal cal has two functions, dc clamping of the ccdin and refin inputs and gating the auto-calibration logic. using "cal only" line timing enables the de- signer to eliminate the requirement of providing a clamp timing signal to the xrd98l59.
xrd98l59 20 rev. 2.00 most timing generators (tg?s) define the start of line and end of line ob pixels on the ccd array. the cal timing signal should always be active for the greatest number of ob pixels possible, either during start or end of line. the more ob pixels that the xrd98l59 can use for its auto- calibration, the faster it can achieve and maintain calibra- tion. while in ?cal only? line calibration timing mode, clamp needs to be held inactive during the output of active video and ob pixels from the ccd. figure 13 shows the minimum timing requirements for the ?cal only? line calibration timing mode. the inactive state for clamp depends on the clamp-polarity setting (clock reg bit d1). end of line n start of line n+1 active video pixels ob pixels ve rtical shift dummy & ob pixels cal internal dc restore time ccd si g nal active video pixels t cal (min 5 pixels) 4 pixels (d1 = 0) clamp internal black level calibration time t cal - 4 pixels figure 13. example of minimum timing requirements for cal only line calibration mode (cal and clamp polarity are serial port programmable) sdi = 0011 0000 0000 vertical shift reject the clamp input can be used to implement a vertical shift reject function while in ? cal only ? line cali- bration timing mode. the vertical shift rejection, also called preblanking, can be used to reject and any large transients present in the ccd output during the vertical clocking. to implement the vertical shift reject (preblanking) function on the xrd98l59 the clamp opt bit must be low (clock reg d4=0) and the clamp input driven with the preblanking timing signal. the preblanking timing signal, commonly called pblk, is generated by the system timing generator and defines the vertical shift of the ccd (see figure 13a). the preblanking pulse opens the reset reject switches internal to the xrd98l59, see figure 5, thereby rejecting any transients in the ccd output while the vertical shifting is being done.
21 rev. 2.00 xrd98l59 end of line n start of line n+1 active video pixels ob pixels ve rtical shift dummy & ob pixels cal internal dc restore time ccd si g nal active video pixels t cal (min 5 pixels) 4 pixels (d1 = 0) clamp internal black level calibration time t cal - 4 pixels figure 13a. example of vertical shift reject timing using the clamp input while in ?cal only? line calibration mode. (cal and clamp polarity are serial port programmable) sdi = 0011 000 0000 32 256 6 ] [ code db gain programmable gain amplifier (pga) pga1 provides gains of 0db, 8db & 16db (1x, 2.5x, and 6.25x). the gain transitions occur at pga gain codes 64d and 128d (40h & 80h). pga2 provides gain from 6db to 22db (2x to 12.5x) with 0.125db steps. the combined pga blocks provide a programmable gain range of 32db. the minimum gain (code 00h) is 6db. the maximum gain (code ffh) is 38db. the following equation can be used to compute pga gain from the gain code: where code is the 8 bit value (0 to 255) programmed in the serial interface gain register. due to device mismatch the gain steps at codes 63 - 64 and 127 - 128 may not be monotonic. analog to digital converter (adc) the analog-to-digital converter is based upon a two-step sub-ranging flash converter architecture with a built in track and hold input stage. the adc conversion is controlled by an internally generated signal, adclk (see figure 10). the adc tracks the output of the pga while adclk is high and holds when adclk is low. this allows maximum time for the pga output to settle to its final value before being sampled. the conversion is then performed and the parallel output is updated, after a 2.5 cycle pipeline delay, on the edge of
xrd98l59 22 rev. 2.00 the adc input node can be accesed for test purposes using the adcin mode (sdi address 0100). use the following procedure to enable the adcin mode: 1) in the serial interface clock register, set the clamp opt bit low (d4). 2) in the serial interface control register, set the adcin bit high (d2). 3) clock sblk & spix to generate internal adc_clk signal. 4) apply adc input signal to ccdin. in this test mode the analog signal, vin, applied to ccdin pin will be converted by the adc. the adc output code is related to vin by the following rules: 1) for vin < vrb, adc output code = 0, 2) for vin > vrt, adc output code = 1023, 3) for vrb < vin < vrt, adc output code = 1024 x (vin - vrb) / (vrt - vrb) control & reset registers adcin bit this bit activates a switch that connects ccdin directly to the adc input. in this mode, the pga output is disabled. see the adc section for details. pd bit (power down) this bit is used to put the chip in the power down mode. it has the same effect as the pd pin. when the pd bit is high the chip will go into the power down mode, all conversions stop. when the pd bit is low the chip is in its normal active mode. in the power down mode the digital output pins are forced to the high impedance mode and the adc reference is disconnected. the serial interface pins remain active in the power down mode. oe bit (output enable) the adc digital output bus is equipped with a high impedance capability. when the oe bit is high the digital outputs are enabled (active). when the oe bit is low the digital outputs are in the high impedance mode (not active). the oe bit only controls the digital output drivers, all other circuits on the chip will remain active. reset bit this bit is used to reset all internal registers to default values. this includes all the serial interface registers as well as the registers in the calibration logic. to reset the chip write a ? 1 ? to the reset bit. the reset bit will clear itself after an internal delay, so there is no need to write a ? 0 ? to the reset bit. the chip also has a power-on-reset function (por) so it will always power up with default values in all registers. it is recommended that the xrd98l59 be reset after power is cycled to avoid loading potentially incorrect serial port data from other asics in the system.
23 rev. 2.00 xrd98l59 black level offset calibration cds 10-bit adc hot pixel clipper pixel averager + coarse accumulator fine accumulator offset calibration logic 10 reg calhold, speedup target offset code gain code db[9:0] 4-bit 10-bit + 10 black level offset calibration loop dns mandac cdac, fdac from serial interface registers ccd signal cdac fdac dns filter - + + figure 15. black level offset calibration block diagram to get the maximum color resolution and dynamic range, the xrd98l59 uses a digitally controlled feedback cir- cuit to correct for offset in the ccd signal as well as offset in the cds, pga & adc signal path. this calibration is done while the ccd outputs optical black (ob) pixels. the cal input signal is used to define when the ccd output contains ob pixels. the calibration logic will take into account the internal pipeline delay.
xrd98l59 24 rev. 2.00 hot pixel clipper ccd ? s occasionally have hot pixels. these are defective pixels which always output a bright level. to ensure the black level is not significantly affected by hot pixels in the ob area, the hot pixel clipper limits pixel data from the adc to a maximum value of 127 (7fh). the hot pixel clipper is only active when cal is active. this clipping only affects the data used by the internal calibration logic. data on the digital output bus db[9:0] is not clipped. pixel averager after the clipper, the logic takes the average of the optical black pixels defined by cal. this averaging function filters noise. offset difference using the target offset register the target offset register (address 0001) value (6 lsb ? s) is subtracted from the ob pixel average. if the difference is positive, the offset dacs are decremented to reduce the effective adc output code. if the difference is negative, the offset dacs are adjusted to increase the effective adc output code. the amount of adjustment is shown in figure 16. set the target offset register value equal to the desired black level output code. for example: set target offset register to code 32 and black ccd outputs are nominally output as 32. default is code 32 decimal. coarse & fine accumulators the coarse and fine accumulators are the registers which hold the digital codes for the coarse and fine offset dacs. the offset dac adjustments are made by adding or subtracting to the value in the fine accumula- tor. if there is an overflow or underflow in the fine accumulator, the fine accumulator is reset to it ? s mid- scale value, and the coarse accumulator is incremented or decremented accordingly. calibration options speed up mode the purpose of this option is to reduce the amount of time required for initial convergence of the calibration feed- back system. the feedback system is designed to have a slow response time to avoid introducing image arti- facts. the slow response time is achieved by limiting the fine accumulator changes to 1 count at a time. the speed up option maintains this slow response while the difference between the averaged adc data and the target offset code is small. but when the difference is larger than 32 lsb ? s the fine accumulator takes large steps. the actual step size depends on the gain code, and is set such that the step will cause no more than a 32 lsb change in the adc output. to activate the speed up mode write a 1 to the speedup bit in the calibration register (bit d3 of serial interface register #5). by default the speedup mode is active. 0.0 0.2 0.4 0.6 0.8 1.0 1.2 1.4 0 64 128 192 256 pga code adc lsb s v dd = 3.0v figure 16. xrd98l59 offset dac step size in adc output lsbs
25 rev. 2.00 xrd98l59 digital noise supression (dns filter) to activate the dns mode, a "1" is written to dns1 bit in the calibration register (bit d2 of serial interface register #5). by default the dns mode is active. in dns mode, the user has the option to select narrow band or wide band noise suppression filters by setting dns0 bit to a "1" (narrow) or "0" (wide) respectively. best performance is achieved by setting dns1 = "1" and dns0 = "0". hold mode the purpose of this mode is to prevent any changes in the fine or coarse accumulators. the idea is to first run the calibration normaly so the fine and coarse accumulators converge on the programmed target offset code. then, just before acquiring the final image data, activate the hold mode. this will ensure the black level offset of the cds/pga does not change while the final image is being transferred out of the ccd. once the image has been acquired from the ccd, turn off the hold mode so the chip can continue to compensate for any changes in offset due to temperature drift or other effects. to activate the hold mode write a 1 to the cal hold bit in the calibration register (bit d4 of serial interface register #5). by default the hold mode is not active. manual mode the purpose of this mode is to disable the automatic calibration feature. in the manual mode, the coarse accumulator is programmed by writing to the cdac register, the fine accumulator is programmed by writing to the fdac register. the fine accumulator is a 10 bit register, but the serial interface registers are only 8 bits wide. as shown in the serial interface register address map, two serial interface registers are concatenated to provide 10 bits to the fine accumulator. to activate the manual mode write a 1 to the mandac bit in the calibration register (bit d0 of serial interface register #5). by default the manual mode is not active.
xrd98l59 26 rev. 2.00 av dd 4-6 3 3 timing generator v driver ccd 5-10 ? 0.01 f 0.01 f 0.1 f 0.1 f 12v clob cldm shd shp serial ports asic/dsp 10-bit digital video input xrd98l59 spix cal clamp 12 11 10 9 8 7 4 6 5 15 16 18 19 20 21 22 23 24 14 25 28 ccdin refin agnd vrb db7 db8 db9 ov dd db6 db5 dv dd vrt sclk load sdi pd dgnd av dd sblk db1 db0 db2 db3 db4 ognd 27 26 17 13 1 2 3 av dd av dd figure 17. application diagram; asic with external timing generator
27 rev. 2.00 xrd98l59 av dd av dd 4-6 3 v driver ccd 5-10 ? 0.01 f 0.01 f 0.1 f 0.1 f 12v serial port asic/dsp 10-bit digital video input xrd98l59 spix cal clamp 1 12 11 10 9 8 7 4 6 5 15 16 18 19 20 21 22 23 24 14 25 28 ccdin refin agnd vrb db7 db8 db9 ovdd db6 db5 dvdd vrt sclk load sdi pd dgnd avdd sblk db1 db0 db2 db3 db4 ognd 27 26 17 13 intenal timing generator 3 2 av dd figure 18. application diagram; asic with internal timing generator
xrd98l59 28 rev. 2.00 figure 19. pga gain vs. gain code gain code pga gain (db) 36 34 32 30 28 26 24 22 20 18 16 14 12 10 8 6 4 0 20 40 60 80 100 120 160 180 200 220 240 255 140
29 rev. 2.00 xrd98l59 30 32 34 36 38 40 42 44 46 0 2 4 6 8 10121416182022242628 sampling frequency (mhz) i dd (av dd + dv dd ) (ma) v dd = 3.0v figure 20. idd vs sample rate
xrd98l59 30 rev. 2.00 30 35 40 45 50 55 60 65 70 0 63 64 127 128 255 gain code snr (db ) figure 21. typical snr vs gain at 20mhz sample rate snr = 20 log (full scale voltage/rms noise)
31 rev. 2.00 xrd98l59 -0.6 -0.4 -0.2 0 0.2 0.4 0.6 0.8 0 128 256 384 512 640 768 896 1024 code lsb figure 22. adc only dnl
xrd98l59 32 rev. 2.00 figure 23. xrd98l59 1.45 mpixel camera reference schematic (sheet 1)
33 rev. 2.00 xrd98l59 figure 24. xrd98l59 1.45 mpixel camera reference schematic (sheet 2)
xrd98l59 34 rev. 2.00 figure 25. xrd98l59 2.31 mpixel camera reference schematic (sheet 1)
35 rev. 2.00 xrd98l59 figure 26. xrd98l59 2.31 mpixel camera reference schematic (sheet 2)
xrd98l59 36 rev. 2.00 28 lead thin shrink small outline (4.4mm tssop) rev. 2.00 e d e h b a 1 seating plane 28 15 14 1 a l c symbol min max min max a 0.033 0.047 0.85 1.20 a1 0.002 0.006 0.05 0.15 a2 0.031 0.041 0.80 1.05 b 0.007 0.012 0.19 0.30 c 0.004 0.008 0.09 0.20 d 0.378 0.386 9.60 9.80 e 0.169 0.177 4.30 4.50 e 0.0256 bsc 0.65 bsc h 0.248 0.256 6.30 6.50 l 0.018 0.030 0.45 0.75 0 8 0 8 millimeters inches note: the control dimension is in millimeter column a 2
37 rev. 2.00 xrd98l59 notice exar corporation reserves the right to make changes to the products contained in this publication in order to improve design, performance or reliability. exar corporation assumes no responsibility for the use of any circuits described herein, conveys no license under any patent or other right, and makes no representation that the circuits are free of patent infringement. charts and schedules contained here in are only for illustration purposes and may vary depending upon a user ? s specific application. while the information in this publication has been carefully checked; no responsibility, however, is assumed for in accuracies. exar corporation does not recommend the use of any of its products in life support applications where the failure or malfunction of the product can reasonably be expected to cause failure of the life support system or to significantly affect its safety or effectiveness. products are not authorized for use in such applications unless exar corporation receives, in writing, assurances to its satisfaction that: (a) the risk of injury or damage has been minimized; (b) the user assumes all such risks; (c) potential liability of exar corporation is adequately protected under the circumstances. copyright 2001 exar corporation datasheet january 2001 reproduction, in part or whole, without the prior written consent of exar corporation is prohibited.

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